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MC33033 Schematic ( PDF Datasheet ) - ON Semiconductor

Teilenummer MC33033
Beschreibung Brushless DC Motor Controller
Hersteller ON Semiconductor
Logo ON Semiconductor Logo 




Gesamt 27 Seiten
MC33033 Datasheet, Funktion
MC33033, NCV33033
Brushless DC
Motor Controller
The MC33033 is a high performance second generation, limited
feature, monolithic brushless dc motor controller which has evolved
from ON Semiconductor’s full featured MC33034 and MC33035
controllers. It contains all of the active functions required for the
implementation of open loop, three or four phase motor control. The
device consists of a rotor position decoder for proper commutation
sequencing, temperature compensated reference capable of supplying
sensor power, frequency programmable sawtooth oscillator, fully
accessible error amplifier, pulse width modulator comparator, three
open collector top drivers, and three high current totem pole bottom
drivers ideally suited for driving power MOSFETs. Unlike its
predecessors, it does not feature separate drive circuit supply and
ground pins, brake input, or fault output signal.
Included in the MC33033 are protective features consisting of
undervoltage lockout, cycle−by−cycle current limiting with a
selectable time delayed latched shutdown mode, and internal thermal
shutdown.
Typical motor control functions include open loop speed, forward or
reverse direction, and run enable. The MC33033 is designed to operate
brushless motors with electrical sensor phasings of 60°/300° or
120°/240°, and can also efficiently control brush dc motors.
Features
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10 to 30 V Operation
Undervoltage Lockout
6.25 V Reference Capable of Supplying Sensor Power
Fully Accessible Error Amplifier for Closed Loop Servo
Applications
High Current Drivers Can Control External 3−Phase MOSFET
Bridge
Cycle−By−Cycle Current Limiting
Internal Thermal Shutdown
Selectable 60°/300° or 120°/240° Sensor Phasings
Also Efficiently Control Brush DC Motors with External MOSFET
H−Bridge
NCV Prefix for Automotive and Other Applications Requiring Site
and Control Changes
Pb−Free Packages are Available
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PDIP−20
P SUFFIX
CASE 738
SO−20L
DW SUFFIX
CASE 751D
20
1
20
1
PIN CONNECTIONS
Top Drive
Output
BT 1
AT 2
Fwd/Rev 3
Sensor
Inputs
SA 4
SB 5
SC 6
Reference Output 7
Oscillator 8
Error Amp
Non Inverting Input
Error Amp
Inverting Input
9
10
20 CT
19 Output Enable
18 60°/120° Select
17 AB
16 BB
15 CB
Bottom
Drive
Outputs
14 VCC
13 Gnd
12
Current Sense
Non Inverting Input
11 Error Amp Out/
PWM Input
(Top View)
ORDERING INFORMATION
See detailed ordering and shipping information in the package
dimensions section on page 25 of this data sheet.
DEVICE MARKING INFORMATION
See general marking information in the device marking
section on page 25 of this data sheet.
© Semiconductor Components Industries, LLC, 2007
January, 2007 − Rev. 9
1
Publication Order Number:
MC33033/D






MC33033 Datasheet, Funktion
MC33033, NCV33033
100 4.0
VCC = 20 V
TA = 25°C
VCC = 20 V
2.0 RT = 4.7 k
CT = 10 nF
10 0
CT = 100 nF
CT = 10 nF
CT = 1.0 nF
0
1.0 10 100 1000
RT, TIMING RESISTOR (kΩ)
Figure 2. Oscillator Frequency versus
Timing Resistor
− 2.0
− 4.0
− 55
− 25 0 25 50 75 100
TA, AMBIENT TEMPERATURE (°C)
Figure 3. Oscillator Frequency Change
versus Temperature
125
56
48
40
32
24
16
8.0
VCC = 20 V
VO = 3.0 V
0 RL = 15 k
− 8.0
CL = 100 pF
TA = 25°C
−16
− 24
1.0 k
10 k
Phase
Gain
100 k
1.0 M
f, FREQUENCY (Hz)
40
60
80
100
120
140
160
180
200
220
240
10M
Figure 4. Error Amp Open Loop Gain and
Phase versus Frequency
0
Vref
− 0.8 Source Saturation
(Load to Ground)
−1.6
VCC = 20 V
TA = 25°C
1.6
0.8
Gnd
Sink Saturation
(Load to Vref)
0
0 1.0 2.0 3.0 4.0 5.0
IO, OUTPUT LOAD CURRENT (mA)
Figure 5. Error Amp Output Saturation
Voltage versus Load Current
AV = +1.0
3.05
No Load
TA = 25°C
3.0
2.95
1.0 μs/DIV
Figure 6. Error Amp Small−Signal
Transient Response
AV = +1.0
4.5
No Load
TA = 25°C
3.0
1.5
5.0 μs/DIV
Figure 7. Error Amp Large−Signal
Transient Response
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MC33033 pdf, datenblatt
MC33033, NCV33033
Inputs (Note 2)
Outputs (Note 3)
Sensor Electrical Phasing (Note 4)
Top Drives
Bottom Drives
60° 120°
Current
SA SB SC SA SB SC F/R Enable Sense AT BT CT AB BB CB
100100
1
1
0 011001
110110
1
1
0 101001
111010
1
1
0 101100
011011
1
1
0 110100
001001
1
1
0 110010
000101
1
1
0 011010
100100
0
1
0 110100
110110
0
1
0 110010
111010
0
1
0 011010
011011
0
1
0 011001
001001
0
1
0 101001
000101
0
1
0 101100
101111
X
X
X 111000
010000
X
X
X 111000
VVVVVV
X
0
X 111000
VVVVVV
X
1
1 111000
(Note 5)
F/R = 1
(Note 5)
F/R = 0
(Note 6)
(Note 7)
(Note 8)
NOTES: 1. V = Any one of six valid sensor or drive combinations.
X = Don’t care.
2. The digital inputs (Pins 3, 4, 5, 6, 18, 19) are all TTL compatible. The current sense input (Pin 12) has a 100 mV threshold with respect to Pin 13. A
logic 0 for this input is defined as < 85 mV, and a logic 1 is > 115 mV.
3. The top drive outputs are open collector design and active in the low (0) state.
4. With 60°/120° (Pin 18) in the high (1) state, configuration is for 60° sensor electrical phasing inputs. With Pin 18 in the low (0) state, configuration is
for 120° sensor electrical phasing inputs.
5. Valid 60° or 120° sensor combinations for corresponding valid top and bottom drive outputs.
6. Invalid sensor inputs; All top and bottom drives are off.
7. Valid sensor inputs with enable = 0; All top and bottom drives are off.
8. Valid sensor inputs with enable and current sense = 1; All top and bottom drives are off.
Figure 20. Three Phase, Six Step Commutation Truth Table (Note 1)
Current Limit
Continuous operation of a motor that is severely
over−loaded results in overheating and eventual failure.
This destructive condition can best be prevented with the use
of cycle−by−cycle current limiting. That is, each on−cycle
is treated as a separate event. Cycle−by−cycle current
limiting is accomplished by monitoring the stator current
build−up each time an output switch conducts, and upon
sensing an over current condition, immediately turning off
the switch and holding it off for the remaining duration of
oscillator ramp−up period. The stator current is converted to
a voltage by inserting a ground−referenced sense resistor RS
(Figure 35) in series with the three bottom switch transistors
(Q4, Q5, Q6). The voltage developed across the sense
resistor is monitored by the current sense input (Pin 12), and
compared to the internal 100 mV reference. If the current
sense threshold is exceeded, the comparator resets the lower
latch and terminates output switch conduction. The value for
the sense resistor is:
RS
+
0.1
Istator(max)
The dual−latch PWM configuration ensures that only one
single output conduction pulse occurs during any given
oscillator cycle, whether terminated by the output of the
Error Amplifier or the current limit comparator.
Reference
The on−chip 6.25 V regulator (Pin 7) provides charging
current for the oscillator timing capacitor, a reference for the
Error Amplifier, and can supply 20 mA of current suitable
for directly powering sensors in low voltage applications. In
higher voltage applications it may become necessary to
transfer the power dissipated by the regulator off the IC. This
is easily accomplished with the addition of an external pass
transistor as shown in Figure 22. A 6.25 V reference level
was chosen to allow implementation of the simpler NPN
circuit, where Vref − VBE exceeds the minimum voltage
required by Hall Effect sensors over temperature. With
proper transistor selection, and adequate heatsinking, up to
one amp of load current can be obtained.
Undervoltage Lockout
A dual Undervoltage Lockout has been incorporated to
prevent damage to the IC and the external power switch
transistors. Under low power supply conditions, it
guarantees that the IC and sensors are fully functional, and
that there is sufficient Bottom Drive Output voltage. The
positive power supply to the IC (VCC) is monitored to a
threshold of 8.9 V. This level ensures sufficient gate drive
necessary to attain low RDS(on) when interfacing with
standard power MOSFET devices. When directly powering
the Hall sensors from the reference, improper sensor
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