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AD8001 Schematic ( PDF Datasheet ) - Analog Devices

Teilenummer AD8001
Beschreibung Current Feedback Amplifier
Hersteller Analog Devices
Logo Analog Devices Logo 




Gesamt 17 Seiten
AD8001 Datasheet, Funktion
a
800 MHz, 50 mW
Current Feedback Amplifier
AD8001
FEATURES
Excellent Video Specifications (RL = 150 , G = +2)
Gain Flatness 0.1 dB to 100 MHz
0.01% Differential Gain Error
0.025؇ Differential Phase Error
Low Power
5.5 mA Max Power Supply Current (55 mW)
High Speed and Fast Settling
880 MHz, –3 dB Bandwidth (G = +1)
440 MHz, –3 dB Bandwidth (G = +2)
1200 V/s Slew Rate
10 ns Settling Time to 0.1%
Low Distortion
–65 dBc THD, fC = 5 MHz
33 dBm Third Order Intercept, F1 = 10 MHz
–66 dB SFDR, f = 5 MHz
High Output Drive
70 mA Output Current
Drives Up to 4 Back-Terminated Loads (75 Each)
While Maintaining Good Differential Gain/Phase
Performance (0.05%/0.25؇)
APPLICATIONS
A-to-D Drivers
Video Line Drivers
Professional Cameras
Video Switchers
Special Effects
RF Receivers
GENERAL DESCRIPTION
The AD8001 is a low power, high speed amplifier designed
to operate on ± 5 V supplies. The AD8001 features unique
9
6
G = +2
3 RL = 100
0
–3
–6
VS = ؎5V
RFB = 820
VS = ؎5V
RFB = 1k
–9
–12
10M
100M
FREQUENCY – Hz
1G
Figure 1. Frequency Response of AD8001
REV. D
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties that
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective companies.
FUNCTIONAL BLOCK DIAGRAMS
8-Lead PDIP (N-8),
5-Lead SOT-23-5
CERDIP (Q-8) and SOIC (R-8)
(RT-5)
NC 1
8 NC
–IN 2
7 V+
+IN 3
6 OUT
V– 4 AD8001 5 NC
AD8001
VOUT 1
5 +VS
–VS 2
+IN 3
4 –IN
NC = NO CONNECT
transimpedance linearization circuitry. This allows it to drive
video loads with excellent differential gain and phase perfor-
mance on only 50 mW of power. The AD8001 is a current
feedback amplifier and features gain flatness of 0.1 dB to 100 MHz
while offering differential gain and phase error of 0.01% and
0.025°. This makes the AD8001 ideal for professional video
electronics such as cameras and video switchers. Additionally,
the AD8001’s low distortion and fast settling make it ideal for
buffer high speed A-to-D converters.
The AD8001 offers low power of 5.5 mA max (VS = ± 5 V) and
can run on a single +12 V power supply, while being capable of
delivering over 70 mA of load current. These features make this
amplifier ideal for portable and battery-powered applications
where size and power are critical.
The outstanding bandwidth of 800 MHz along with 1200 V/µs
of slew rate make the AD8001 useful in many general-purpose
high speed applications where dual power supplies of up to ± 6 V
and single supplies from 6 V to 12 V are needed. The AD8001 is
available in the industrial temperature range of –40°C to +85°C.
Figure 2. Transient Response of AD8001; 2 V Step, G = +2
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
www.analog.com
Fax: 781/326-8703 © 2003 Analog Devices, Inc. All rights reserved.






AD8001 Datasheet, Funktion
9
6
G = +2
3 RL = 100
0
–3
–6
VS = ؎5V
RFB = 820
VS = ؎5V
RFB = 1k
–9
–12
10M
100M
FREQUENCY – Hz
1G
TPC 7. Frequency Response, G = +2
0.1
0
–0.1
RF = 698
RF =
649
–0.2
–0.3
–0.4
–0.5
G = +2
RL = 100
VIN = 50mV
RF = 750
–0.6
–0.7
–0.8
–0.9
1M
10M
FREQUENCY – Hz
100M
TPC 8. 0.1 dB Flatness, R Package (for N Package Add
50 to RF)
–50
VOUT = 2V p-p
–60 RL = 1k
G = +2
؎5V SUPPLIES
–70
SECOND HARMONIC
–80
–90 THIRD HARMONIC
–100
–110
10k
100k
1M
FREQUENCY – Hz
10M
100M
TPC 9. Distortion vs. Frequency, RL = 1 k
1000
800
600
400
200
VS = ؎5V
RL = 100
G = +2
R
PACKAGE
AD8001
N
PACKAGE
0
500 600 700 800 900
VALUE OF FEEDBACK RESISTOR (RF) –
TPC 10. –3 dB Bandwidth vs. RF
1000
–50
؎5V SUPPLIES
–60 VOUT = 2V p-p
RL = 100
G = +2
–70
SECOND HARMONIC
–80
–90
THIRD HARMONIC
–100
10k
100k
1M
FREQUENCY – Hz
10M
100M
TPC 11. Distortion vs. Frequency, RL = 100
0.08
0.06
0.04
0.02
0.00
0.02
0.01
0.00
–0.01
–0.02
G = +2
RF = 806
2 BACK TERMINATED
LOADS (75)
1 BACK TERMINATED
LOAD (150)
1 AND 2 BACK TERMINATED
LOADS (150AND 75)
0 100
IRE
TPC 12. Differential Gain and Differential Phase
REV. D
–5–

6 Page









AD8001 pdf, datenblatt
AD8001
Printed Circuit Board Layout Considerations
As to be expected for a wideband amplifier, PC board parasitics
can affect the overall closed-loop performance. Of concern are
stray capacitances at the output and the inverting input nodes. If
a ground plane is to be used on the same side of the board as
the signal traces, a space (5 mm min) should be left around the
signal lines to minimize coupling. Additionally, signal lines
connecting the feedback and gain resistors should be short
enough so that their associated inductance does not cause high
frequency gain errors. Line lengths on the order of less than
5 mm are recommended. If long runs of coaxial cable are being
driven, dispersion and loss must be considered.
Power Supply Bypassing
Adequate power supply bypassing can be critical when optimiz-
ing the performance of a high frequency circuit. Inductance in
the power supply leads can form resonant circuits that produce
peaking in the amplifier’s response. In addition, if large current
transients must be delivered to the load, then bypass capacitors
(typically greater than 1 µF) will be required to provide the best
settling time and lowest distortion. A parallel combination of
4.7 µF and 0.1 µF is recommended. Some brands of electrolytic
capacitors will require a small series damping resistor 4.7 for
optimum results.
DC Errors and Noise
There are three major noise and offset terms to consider in a
current feedback amplifier. For offset errors, refer to the equation
below. For noise error the terms are root-sum-squared to give a
net output error. In the circuit in Figure 7 they are input offset
(VIO), which appears at the output multiplied by the noise gain
of the circuit (1 + RF/RI), noninverting input current (IBN × RN)
also multiplied by the noise gain, and the inverting input current,
which when divided between RF and RI and subsequently
multiplied by the noise gain always appears at the output as
IBN × RF. The input voltage noise of the AD8001 is a low 2 nV/
Hz. At low gains though the inverting input current noise times
RF is the dominant noise source. Careful layout and device
matching contribute to better offset and drift specifications for
the AD8001 compared to many other current feedback ampli-
fiers. The typical performance curves in conjunction with the
following equations can be used to predict the performance of
the AD8001 in any application.
VOUT
= VIO
× 1 +
RF
± I BN
× RN
× 1 +
RF
± I BI
× RF
RI
RI
RF
RI IBI
RN IBN
VOUT
Driving Capacitive Loads
The AD8001 was designed primarily to drive nonreactive loads.
If driving loads with a capacitive component is desired, best
frequency response is obtained by the addition of a small series
resistance, as shown in Figure 8. The accompanying graph
shows the optimum value for RSERIES versus capacitive load. It is
worth noting that the frequency response of the circuit when
driving large capacitive loads will be dominated by the passive
roll-off of RSERIES and CL.
909
RSERIES
IN
RL
500
CL
Figure 8. Driving Capacitive Loads
40
G = +1
30
20
10
0
0 5 10 15 20 25
CL – pF
Figure 9. Recommended RSERIES vs. Capacitive Load
Figure 7. Output Offset Voltage
REV. D
–11–

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