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AD810 Schematic ( PDF Datasheet ) - Analog Devices

Teilenummer AD810
Beschreibung Low Power Video Op Amp
Hersteller Analog Devices
Logo Analog Devices Logo 




Gesamt 17 Seiten
AD810 Datasheet, Funktion
a
Low Power
Video Op Amp with Disable
FEATURES
High Speed
80 MHz Bandwidth (3 dB, G = +1)
75 MHz Bandwidth (3 dB, G = +2)
1000 V/s Slew Rate
50 ns Settling Time to 0.1% (VO = 10 V Step)
Ideal for Video Applications
30 MHz Bandwidth (0.1 dB, G = +2)
0.02% Differential Gain
0.04؇ Differential Phase
Low Noise
2.9 nV/Hz Input Voltage Noise
13 pA/Hz Inverting Input Current Noise
Low Power
8.0 mA Supply Current max
2.1 mA Supply Current (Power-Down Mode)
High Performance Disable Function
Turn-Off Time 100 ns
Break Before Make Guaranteed
Input to Output Isolation of 64 dB (OFF State)
Flexible Operation
Specified for ؎5 V and ؎15 V Operation
؎2.9 V Output Swing Into a 150 Load (VS = ؎5 V)
APPLICATIONS
Professional Video Cameras
Multimedia Systems
NTSC, PAL & SECAM Compatible Systems
Video Line Driver
ADC/DAC Buffer
DC Restoration Circuits
PHASE
GAIN = +2
RL = 150
0
–45
–90
1 –135
0
VS = ±15V
–180
GAIN
–1
–2
VS = ±15V
–3
±5V
±2.5V
–225
–270
±5V
–4
±2.5V
–5
1 10 100 1000
FREQUENCY – MHz
Closed-Loop Gain and Phase vs. Frequency, G = +2,
RL = 150, RF = 715
REV. A
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
AD810
CONNECTION DIAGRAM
8-Pin Plastic Mini-DIP (N), SOIC (R)
and Cerdip (Q) Packages
OFFSET
NULL 1
–IN 2
+IN 3
–VS 4
AD810
TOP VIEW
8 DISABLE
7 +VS
6 OUTPUT
5
OFFSET
NULL
PRODUCT DESCRIPTION
The AD810 is a composite and HDTV compatible, current
feedback, video operational amplifier, ideal for use in systems
such as multimedia, digital tape recorders and video cameras.
The 0.1 dB flatness specification at bandwidth of 30 MHz
(G = +2) and the differential gain and phase of 0.02% and
0.04° (NTSC) make the AD810 ideal for any broadcast quality
video system. All these specifications are under load conditions
of 150 (one 75 back terminated cable).
The AD810 is ideal for power sensitive applications such as
video cameras, offering a low power supply current of 8.0 mA
max. The disable feature reduces the power supply current to
only 2.1 mA, while the amplifier is not in use, to conserve
power. Furthermore the AD810 is specified over a power supply
range of ± 5 V to ± 15 V.
The AD810 works well as an ADC or DAC buffer in video
systems due to its unity gain bandwidth of 80 MHz. Because the
AD810 is a transimpedance amplifier, this bandwidth can be
maintained over a wide range of gains while featuring a low
noise of 2.9 nV/Hz for wide dynamic range applications.
0.10
0.09
0.08
0.07
0.06
0.05
0.04
0.03
0.02
0.01
0
5
0.20
GAIN = +2
RF = 715
RL = 150
fC = 3.58MHz
100 IRE
MODULATED RAMP
0.18
0.16
0.14
0.12
GAIN
PHASE
0.10
0.08
0.06
0.04
0.02
0
6 7 8 9 10 11 12 13 14 15
SUPPLY VOLTAGE – ± Volts
Differential Gain and Phase vs. Supply Voltage
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700
Fax: 617/326-8703






AD810 Datasheet, Funktion
250
200
VS = ±15V
150
100
VS = ±5V
50
–60 –40 –20 0 +20 +40 +60 +80 +100 +120 +140
JUNCTION TEMPERATURE – °C
Figure 7. Short Circuit Current vs. Temperature
Typical Characteristics– AD810
120
100
VS = ±15V
80
60
VS = ± 5V
40
20
–60 –40 –20 0 +20 +40 +60 +80 +100 +120 +140
JUNCTION TEMPERATURE – °C
Figure 8. Linear Output Current vs. Temperature
10.0
1.0
GAIN = 2
RF = 715
VS = ±5V
VS = ±15V
0.1
1M
100k
10k
1k
0.01
10k
100k
1M
FREQUENCY – Hz
10M
100M
Figure 9. Closed-Loop Output Resistance vs. Frequency
100
100k
1M 10M
FREQUENCY – Hz
100M
Figure 10. Output Resistance vs. Frequency,
Disabled State
30
25
±
VS = ±15V
20 OUTPUT LEVEL FOR 3% THD
RL = 400
15
10
VS = ±5V
5
0
100k
1M 10M
FREQUENCY – Hz
100M
Figure 11. Large Signal Frequency Response
100
VS = ±5V TO ±15V
100
INVERTING INPUT
CURRENT NOISE
10 10
VOLTAGE NOISE
NONINVERTING INPUT
CURRENT NOISE
11
10 100 1k 10k 100k
FREQUENCY – Hz
Figure 12. Input Voltage and Current Noise vs. Frequency
REV. A
–5–

6 Page









AD810 pdf, datenblatt
Applications– AD810
GENERAL DESIGN CONSIDERATIONS
The AD810 is a current feedback amplifier optimized for use in
high performance video and data acquisition systems. Since it
uses a current feedback architecture, its closed-loop bandwidth
depends on the value of the feedback resistor. Table I below
contains recommended resistor values for some useful closed-
loop gains and supply voltages. As you can see in the table, the
closed-loop bandwidth is not a strong function of gain, as it
would be for a voltage feedback amp. The recommended
resistor values will result in maximum bandwidths with less than
0.1 dB of peaking in the gain vs. frequency response.
The –3 dB bandwidth is also somewhat dependent on the power
supply voltage. Lowering the supplies increases the values of
internal capacitances, reducing the bandwidth. To compensate
for this, smaller values of feedback resistor are sometimes used
at lower supply voltages. The characteristic curves illustrate that
bandwidths of over 100 MHz on 30 V total and over 50 MHz
on 5 V total supplies can be achieved.
Table I. –3 dB Bandwidth vs. Closed-Loop Gain and
Resistance Values (RL = 150 )
VS = ؎15 V
Closed-Loop
Gain
+1
+2
+10
–1
–10
VS = ؎5 V
Closed-Loop
Gain
+1
+2
+10
–1
–10
RFB
1 k
715
270
681
249
RFB
910
715
270
620
249
RG
715
30
681
24.9
RG
715
30
620
24.9
–3 dB BW
(MHz)
80
75
65
70
65
–3 dB BW
(MHz)
50
50
50
55
50
ACHIEVING VERY FLAT GAIN RESPONSE AT
HIGH FREQUENCY
Achieving and maintaining gain flatness of better than 0.1 dB
above 10 MHz is not difficult if the recommended resistor
values are used. The following issues should be considered to
ensure consistently excellent results.
CHOICE OF FEEDBACK AND GAIN RESISTOR
Because the 3 dB bandwidth depends on the feedback resistor,
the fine scale flatness will, to some extent, vary with feedback
resistor tolerance. It is recommended that resistors with a 1%
tolerance be used if it is desired to maintain exceptional flatness
over a wide range of production lots.
PRINTED CIRCUIT BOARD LAYOUT
As with all wideband amplifiers, PC board parasitics can affect
the overall closed-loop performance. Most important are stray
capacitances at the output and inverting input nodes. (An added
capacitance of 2 pF between the inverting input and ground will
add about 0.2 dB of peaking in the gain of 2 response, and
increase the bandwidth to 105 MHz.) A space (3/16" is plenty)
should be left around the signal lines to minimize coupling.
Also, signal lines connecting the feedback and gain resistors
should be short enough so that their associated inductance does
not cause high frequency gain errors. Line lengths less than 1/4"
are recommended.
QUALITY OF COAX CABLE
Optimum flatness when driving a coax cable is possible only
when the driven cable is terminated at each end with a resistor
matching its characteristic impedance. If coax were ideal, then
the resulting flatness would not be affected by the length of the
cable. While outstanding results can be achieved using
inexpensive cables, some variation in flatness due to varying
cable lengths is to be expected.
POWER SUPPLY BYPASSING
Adequate power supply bypassing can be critical when
optimizing the performance of a high frequency circuit.
Inductance in the power supply leads can contribute to resonant
circuits that produce peaking in the amplifier's response. In
addition, if large current transients must be delivered to the
load, then bypass capacitors (typically greater than 1 µF) will be
required to provide the best settling time and lowest distortion.
Although the recommended 0.1 µF power supply bypass
capacitors will be sufficient in most applications, more elaborate
bypassing (such as using two paralleled capacitors) may be
required in some cases.
POWER SUPPLY OPERATING RANGE
The AD810 will operate with supplies from ± 18 V down to
about ± 2.5 V. On ± 2.5 V the low distortion output voltage
swing will be better than 1 V peak to peak. Single supply
operation can be realized with excellent results by arranging for
the input common-mode voltage to be biased at the supply
midpoint.
OFFSET NULLING
A 10 kpot connected between Pins 1 and 5, with its wiper
connected to V+, can be used to trim out the inverting input
current (with about ± 20 µA of range). For closed-loop gains
above about 5, this may not be sufficient to trim the output
offset voltage to zero. Tie the pot's wiper to ground through a
large value resistor (50 kfor ± 5 V supplies, 150 kfor ± 15 V
supplies) to trim the output to zero at high closed-loop gains.
REV. A
–11–

12 Page





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